Crest Factor Reduction for OFDM Using Selective Subcarrier Degradation

    R. Neil Braithwaite

[Abstract]This paper describes a crest factor reduction (CFR) method that reduces peaks in the time domain by modifying selected data subcarriers within an OFDM signal. The data subcarriers selected for modification vary with each symbol interval and are limited to those subcarriers whose data elements are mapped onto the outer boundary of the constellation. In the proposed method, a set of peaks are identified within an OFDM symbol interval. Data subcarriers whose data element has a positive or negative correlation with the set peak are selected. For a subcarrier with an outer element and a significant positive correlation, a bit error (reversal) is intentionally introduced. This moves the data element to the opposite side of the constellation. Outer elements on negatively-correlated subcarriers are increased in magnitude along the real or imaginary axis. Experimental results show that selecting the correct subcarriers for bit reversals and outward enhancements reduces the peak-to-average power ratio (PAPR) of the OFDM signal to a target value and limits in-band degradation measured by bit error rate (BER) and error vector magnitude (EVM).

[Keywords] crest factor reduction; OFDM; PAPR; wireless communication system; digital transmitter

 

 

1 Introduction
    Orthogonal frequency-division multiplexing (OFDM) waveforms can have large peak-to-average power ratios (PAPR). Crest factor reduction (CFR) reduces peaks at the expense of signal quality. Usually, degradation is distributed throughout the signal’s frequency bandwidth in the form of spectral leakage and in-band errors. However, because the OFDM signal is created in the Fourier domain, degradation can be concentrated to specific subcarriers (frequency bins of the FFT).


    In the proposed method, CFR is used sparingly to bound the PAPR when transmitting at high power levels. This differs from the usual approach of maximizing PAPR reduction. The bound is met, and bit error rate (BER) is limited without deviating from the OFDM standard — for example, Worldwide Interoperability for Microwave Access (WiMAX) 802.16 [1]. This peak power bound allows the power amplifier (PA) in the transmitter to be designed for greater power-added efficiency (PAE) [2]. It may be necessary to enforce a second PAPR bound if the dynamic range of the digital-to-analog converter (DAC) cannot prevent clipping for all possible signals.


    The remainder of this introduction describes OFDM signal generation as well as the subcarrier phase alignments that create peaks. Section 2 contains a review of CFR methods. Section 3 introduces new CFR methods for intentionally degrading selected subcarriers whose data elements are correlated (phase aligned) with the peaks of the OFDM signal. Section 4 contains experimental results that show a WiMAX signal can be crest-factor reduced to a target PAPR by introducing an acceptable amount of in-band degradation. This degradation is measured by the BER and error vector magnitude (EVM).

 

1.1 OFDM Transmit Overview
    Creation of an OFDM symbol for radio frequency (RF) transmission is shown in Fig. 1. The symbol is part of a data stream that has been 1) encoded, 2) modulated, 3) converted from serial to parallel as a 256 sample block, 4) converted to the time domain using an inverse fast Fourier transform (IFFT), 5) extended using a cyclic prefix (CP) to 256 + CP samples, and 6) converted back into a serial data stream. The data stream is then converted from DAC, lowpass filtered, up-converted to RF, then amplified by a PA. The signals Y(k) and y (n) are important for the crest factor method presented in this paper. These symbols correspond to the Fourier domain and time domain data blocks, respectively, of the OFDM symbol.

 


    The encoding includes coders and interleavers to allow for error correction at the receiver. The modulator allows rate changes, and the rate is selected according to the received signal-to-noise ratio (SNR) and BER at the receiver. The rates from lowest to highest are binary phase-shift keying (BPSK), quadrature phase-shift keying (QPSK), 16-quadrature amplitude modulation (16-QAM), and 64-QAM. In the serial-to-parallel conversion, a frequency domain representation is created, and the data elements are assigned to different subcarriers of the OFDM signal. The IFFT transforms the data from the frequency domain to the time domain. The cyclic prefix is a copy of the tail of the time domain block and is appended to the beginning of the time domain block. The cyclic prefix protects against intersymbol interference (ISI) caused by multipath RF propagation.


    Within an OFDM symbol, the subcarriers may be data subcarriers, pilot subcarriers, or null subcarriers. No data elements are mapped onto the null subcarriers, which include the outer guard-band frequencies and the DC subcarrier. The pilots are BPSK-modulated and assigned to specific subcarriers. The remaining subcarriers are used for data transmission, which may be modulated using BPSK, QPSK, 16-QAM, or 64-QAM.


    The OFDM-transmitted signal is a sequence of symbols sent as a down-link (DL) subframe. This subframe comprises a preamble, frame control header (FCH), and DL bursts. QPSK is used for the preamble and BPSK for the FCH. BPSK, QPSK, 16-QAM, or 64-QAM (except for the BPSK pilots) is used for the DL bursts. The preamble and FCH are sent first, and the DL bursts are sent in order of the modulation rates (lower rates are sent first).


    The OFDM symbol at the output is a time-domain data sequence. Although the individual data subcarriers are transmitted using simple modulation mappings, the magnitude in the time domain varies significantly. This is due to the IFFT operation that forms each time-sample from a sum of 200 random-phase variables (56 of the 256 subcarriers are null subcarriers). Phase alignment of subcarriers in the frequency domain results in large peaks in the time domain.
Peak-forming phase alignment in the frequency domain varies according to the position of the peak after the IFFT within the time block. A peak at time t peak within the interval t = [0, 255] is maximized by the following subcarrier phases:

 


where   (N = 256), k  is the subcarrier frequency index (DC = 0), and θ (t peak) is the phase of the complex time sample at t peak.


    The magnitude of the subcarriers also has an effect on peaking. Although the magnitude is constant for BPSK and QPSK, it varies between constellation elements for 16-QAM and 64-QAM. Higher magnitudes are found at the outer elements of the 16-QAM and 64-QAM constellations. As a result, it can be assumed that many of these outer constellation elements are present in the data subcarriers when a large peak appears in the time domain.


2 Crest Factor Reduction
    Large peaks cause problems because PAs become less efficient as the PAPR of the RF signal increases. Limiting the PAPR is necessary for a more efficient transmitter design. This process is called CFR. Past CFR methods for OFDM signals include clip and filter, partial transmit sequence (PTS), selective mapping (SLM), tone reservation, and constellation extension. The following is a summary of these CFR methods and their suitability for OFDM signals.


    The direct CFR method involves clipping peaks of the time signal y (n )when they exceed a specified level, L. The clipped signal y clip(n ) is

 

 

The excess peak waveform
y peaks(n ) becomes

 


    Clipping moves the constellation elements from their assigned positions. The difference between the actual and assigned positions in the IQ space is called the constellation error or EVM. The allowable relative constellation error for WiMAX, averaged over subcarriers, frames, and packets, depends on the rate modulation where the most difficult specification is -31.0 dB for the 3/4 rate 64-QAM. Clipping tends to distribute excess peak energy over the 256 subcarriers, including the null and pilot subcarriers. As well as EVM limits on the data subcarriers, there are also limits on spurious emissions and adjacent channel leakage ratio (ACLR). These limits are specifically for the null subcarriers within the guard-band frequencies. The energy from the clipped peaks must be constrained to reside primarily on the in-band subcarriers.


    Filtering attenuates the excess peak energy present in the null subcarriers (except for the DC subcarrier). That is,

 


    where h (τ ) is a filter kernel. The crest-factor-reduced signal being transmitted, denoted y CFR(n ), becomes

 


    where α is a scaling term used to control the EVM introduced by the CFR [4], [5]. In some clip and filter implementations [6], the excess peak waveform y peaks(n ) is replaced by a sequence of delta functions. Each delta function is located at a peak and assigned a magnitude and phase that match the excess value of the peak. This sequence is filtered using (4).
Using α in (5) for controlling EVM of OFDM signals is not effective because the EVM limit varies according to the function of the subcarrier and the rate modulation of the data (BPSK, QPSK, 16-QAM, or 64-QAM). It is beneficial for the receiver to have accurate pilot information, which means the CFR-induced EVM should be zero for pilot subcarriers. Multiaccess OFDM, such as OFDMA and LTE, may have different rate modulations on different subcarrier blocks. Because the allowable EVM is larger for BPSK and QPSK than for 16-QAM and 64-QAM, some researchers [7] convert the excess peak signal back into the frequency domain and apply the filtering and rate-dependent EVM control by weighting the subcarriers. The result is then converted back into the time domain to produce the desired Δy (n ) and y CFR(n ).


    The EVM control for a data subcarrier depends on the modulation type. CFR attempts to introduce EVM on data subcarriers to reduce peaks without increasing the BER at the receiver. Thus, QPSK allows more EVM than 64-QAM because the distance between neighboring points in the constellation is greater. However, some researchers [8] have exploited the fact that points on the outer boundary of the constellation have no neighbors in the outward-expanding direction. As a result, EVM need not be limited in the outward direction because it does not cause bit errors at the receiver. Outward expansion is also used in the proposed CFR and is discussed in section 3.

 

    In a different class of CFR methods, CFR disrupts the subcarrier phase alignments that create peaks. These methods include partial transmit sequence (PTS) [9]-[11] and selective mapping (SLM) [12]. The subcarriers are multiplied by a set of different phase-shift vectors that produce a set of potential time sequences. The time sequence with the lowest PAPR is transmitted. Information about the phase-shift vector used must be sent to the receiver to allow demodulation. This is considered a disadvantage of the method. A PTS method specifically for LTE and not requiring the phase-shift vector to be sent to the receiver is described in [13]. Neither PTS nor SLM is used in the proposed CFR method.


    A third CFR method involves reserving some of the subcarriers as peak-reducers; that is, the reserved subcarriers do not carry any data. This method is called tone reservation [14], [15]. Once a peak is detected in the time domain, the magnitudes and phases of the reserved subcarriers are selected to reduce the peak. Unfortunately, data throughput is reduced because fewer data subcarriers are available. It is possible to use tone reservation as a form of clip and filter with EVM control. The EVM is set to zero for all data subcarriers that are not reserved for peak reduction. The scale factor, α , may have to be increased above unity for such an implementation in order to compensate for the sparseness of the reserved subcarriers in the frequency domain. Reserved tones are not used in the proposed CFR method.


    A fourth CFR method involves altering the constellation mapping so that elements are not unique. This is referred to as constellation extension [16]. A redundant mapping of input bits is used so that opposing points on the constellation, dIQ and -dIQ, represent the same data at the receiver. The advantage of constellation extension is that π radian phase shifts can be introduced onto some of the subcarriers with the goal of disrupting peak-forming phase alignments. The downside of this method is that one bit is lost in the constellation mapping, which reduces throughput for QPSK, 16-QAM, and 64-QAM to 1/2, 3/4, and 5/6 of the original value, respectively. Also, the Gray code mapping specified in the standard must be abandoned. The proposed CFR method similarly introduces large phase shifts onto selected subcarriers; however, the phase shifts are applied to the standard Gray code mapping instead of using the redundant constellation mapping already described.


3 Proposed CFR Method
    The proposed CFR method does not alter the WiMAX (or other OFDM) standard nor does it require additional information to be sent to the receiver. The accuracy of the null and pilot subcarriers is preserved by restricting constellation errors to selected data subcarriers. CFR modifications are applied only to subcarriers whose data elements are mapped onto the outer positions of the constellation. For BPSK and QPSK, the outer elements include the entire constellation. For 16-QAM and 64-QAM, there are 12 (of 16) and 30 (of 64) outer elements, respectively. The outer elements have special properties in terms of constellation errors and BER. These properties are exploited in the proposed CFR method.


    In a 16-QAM constellation, the IQ mapping and decision boundaries used by the receiver define the relationship between constellation errors and BER. The 16-QAM mapping is a Gray code (Fig. 2). Also shown in Fig. 2 are the decision boundaries of the receiver. It is of interest to determine a) the largest constellation error that can be tolerated without causing a bit error, and b) the largest constellation error caused by a single bit reversal. The number of bit reversals between the actual and received elements is referred to as the Hamming distance.

 


    The largest constellation error that can be tolerated without causing a bit error depends on the position of the data element. A single bit error occurs when the constellation error causes the received element to cross one of the horizontal or vertical boundaries. The distance between an interior element and the closest boundary is Δ/2; however, this allowable error, which includes additive noise, is shared between the transmitter, receiver, and propagation channel. For the outer elements, there is at least one direction where no decision boundary exists: the outward direction away from either the I axis or Q axis (depending on the position within the constellation). At the corner elements, there are two directions unconstrained by decision boundaries. Intentionally increasing the constellation errors for outer elements in these unconstrained directions does not increase the BER [6].


    To determine the largest constellation error caused by a single bit reversal, we need to look at the Gray code mapping. Neighboring elements in the horizontal and vertical directions have a Hamming distance of one. If we assume the actual and received constellation elements differ by a Hamming distance of one, the constellation error for an interior point is Δ. For outer elements, a Hamming distance of unity can produce a constellation error of 3Δ
(Fig. 2). Thus, large constellation errors can be created from a single bit reversal on an outer element.


    Using the CFR method, constellation errors are created. The proposed method concentrates the constellation errors on the data subcarriers that produce the least amount of BER. That is, the goal is to generate as much constellation error as necessary for the CFR while creating the minimum Hamming distance between the actual and received elements. Data subcarriers with outer constellation elements are ideal for CFR.


    Two CFR methods are possible: outward enhancement and bit reversal. The former increases the I- or Q-component magnitude for all data subcarriers that have an outer element and negative correlation to the peak. The latter reverses the sign of the I- or Q-component for subcarriers that have an outer element and large positive correlation to the peak. Because sign reversal causes a bit error, it is used more sparingly than outward enhancement.
As well as reducing the peak value, it is also important not to significantly increase the secondary peaks in the time block. To avoid enhancing secondary peaks, certain subcarriers cannot be used for peak reduction. Only subcarriers with a negative correlation to the primary peak and all secondary peaks are used for the outward enhancements. Only subcarriers with a positive correlation to the primary and secondary peaks are considered for bit reversal. The number of secondary peaks specified must be limited to avoid eliminating too many subcarriers from the CFR process.


    The CFR method is shown in Fig. 3. The OFDM system in Fig. 1 is modified so that the PAPR is measured in the time domain, after the IFFT and before the addition of the cyclic prefix. If the PAPR is small enough (less than 8.5 dB for example), the original OFDM data block is used for transmission. If the PAPR is too large, the CFR OFDM data block is used. Before CFR is applied, the primary and secondary peaks are identified within the time block. The CFR module reduces the primary peak and does not increase the secondary peaks. CFR is applied in the Fourier domain. The CFR signal is then converted to a time block using an IFFT. The CFR OFDM data block is not computed when the PAPR of the original signal y (n ) is below 8.5 dB.
The CFR module is shown in greater detail in Fig. 4. CFR uses the phase alignment profile described by (1) for each of the primary and secondary peaks. The phase alignment profile is cross-correlated with the real and imaginary components of the subcarriers containing outer elements. The cross correlations for tpeak are

 

 

 

 

    The peak is formed by the sum of many subcarriers. Because of the phase term θ (t peak) in (1), subcarriers with positive cross-correlations contribute to the peak whereas those with negative cross-correlations attenuate the peak. Applying a bit reversal, that is, changing the sign of either Re{Y (k )} or Im{Y (k )}) to a subcarrier, reverses the cross-correlation. A positive to negative change reduces the peak. Increasing the magnitude of either
Re{Y (k )} or Im{Y (k )} for a subcarrier possessing a negative cross-correlation also reduces the peak. Thus, a coordinated effort to create or enhance the negative cross-correlation on many subcarriers results in effective CFR.


    There is a risk that a secondary peak will increase in response to the CFR of the primary peak. It would be poor use of bit reversals and outward enhancements if the CFR transformed a secondary peak into a primary peak. To prevent this, the cross-correlations are computed relative to the secondary peaks as well. The intersection of the sets of positively-correlated components for each peak is used as a pool of available subcarriers for a bit reversal. The available subcarrier possessing the largest positive correlation to the peak is selected. The intersection of the negatively-correlated components for each peak is also computed. The outward enhancement is applied to all the available subcarrier components from the negatively-correlated set. The enhancement is a scalar multiple of the original value, for example, 1.05
Re{Y (k )} or 1.05 Im{Y (k )}.


    In this approach, a secondary peak has a magnitude that is above a threshold defined as a fraction of the primary peak. The fraction is determined by the amount of peak reduction sought from the CFR. The potential increase in the secondary peak is directly related to the decrease in the primary peak. Currently, the target PAPR is set to 8.5 dB. When the original PAPR is greater than 8.5, 9.2, or 9.7 dB, the fractional thresholds for secondary peaks are 0.85, 0.8, and 0.75 of the primary peak, respectively. These thresholds were obtained by experimentation.


    Selecting too many secondary peaks can be problematic because the intersection of the correlated subcarrier component sets (Fig. 4) may become a null set, preventing any CFR. To avoid this problem, the fractional threshold for secondary peaks is raised, if necessary, until the number of selected peaks is three or less. For these rare occurrences, the number of bit reversals is reduced to avoid excessively enhancing the secondary peaks, but this comes at the expense of increased PAPR. Thus, to limit the number of secondary peaks considered, it is sometimes necessary to increase the target PAPR for a given block, even if this results in clipping at the PA.


    Because a bit reversal typically reduces the peak by about 0.4 dB, it is necessary to specify additional bit reversals for large peaks. The number of bit reversals for an OFDM symbol is 1, 2, 3, or 4 when the original PAPR exceeds 8.7, 9.2, 9.7, and 10.1 dB, respectively. There are two approaches to implementing N  bit reversals when N > 1. Either all N  bit reversals are applied at once (Fig. 4), or single-bit reversals are applied recursively N  times (Fig. 5). For N = 0 (PAPR < 8.7 dB), only outward enhancement is used.

 


    Single bit reversal applied recursively N  times is shown in Fig. 5. This approach requires additional IFFTs to be computed. Because the primary and secondary peaks are re-computed after each bit reversal, the fractional threshold for the secondary peaks is set to 0.85. Outward expansion is applied after the last bit reversal has been completed.
In addition to bit reversals and outward expansions, a third CFR approach can be used. In this approach, constellation error is distributed over all elements, not just the outer elements. The phase profiles for the primary and secondary peaks are multiplied by a scalar term and then added to the Fourier coefficients. This introduces constellation errors similar to clipping, except that the affected subcarriers are selected, which allows the pilot and null subcarriers to be transmitted without error. Because the phase profiles of the primary and secondary peaks have already been computed (Fig. 4), the additional computational cost is minimal. The size of the scalar term controls the constellation error in this third part of the CFR, and the scalar term is typically selected to be small in value. That is, this is not the primary source of peak reduction. In the proposed CFR method, the third approach is used to assist with reducing the largest peaks. The scale term is made to be an increasing function of the PAPR of the OFDM symbol.


    In the CFR approach shown in Fig. 4, the cross-correlation is computed for all subcarrier components associated with the primary and secondary peaks. If only bit reversals are used for CFR, the cross-correlation for the secondary peak need only be computed for the subcarrier components associated with the primary peak (Fig. 6). This can be thought of as a serial implementation of a correlated subcarrier component search (Fig. 4), which requires fewer computations on average because the set of available subcarrier components becomes smaller as subsequent secondary peaks are tested.

 


4 Results
    The CFR approach in Fig. 4 is applied to a WiMAX DL subframe comprising two QSPK symbols for the preamble, one BPSK symbol for the FCH, and 75 64-QAM payload symbols. The 64-QAM symbols contain BPSK pilot subcarriers. The ratio for the cyclic prefix is 0.125, which corresponds to 32 time samples for the 256 data blocks. The DL subframe is repeated 20 times with random data sent on the data subcarriers.
BER associated with the CFR is caused by the bit reversals only and does not account for the forward error correction (FEC) provided by the bit encoding. The EVM caused by the CFR is measured with

 


    where E[ ] is expected value, and d IQ and d CFR are the data elements within the IQ constellation space before and after CFR, respectively. EVM is measured in two ways: the first uses the original constellation data point for d IQ(n ) whereas the second  defines
d IQ(n ) as the nearest constellation point to d CFR(n ). In the first way, in-band signal degradations associated with both the outward expansion and bit reversals are measured; in the second way, degradation associated with the outward expansion only is measured.
CFR has a target PAPR of 8.5 dB. The PAPR is defined as

 

 

    where y (t ) is the analog output signal after filtering. In practice, however, the PAPR is defined using the digital time domain signal y (n ) and is based on the signal power statistics rather than the absolute peak. The practical peak is the level Po , for which the signal power  y (n ) 2 has a 10β probability of exceeding this peak. The complementary cumulative distribution function (CCDF) of  y (n ) 2  , in which β is plotted as a function of Po, is a useful description of the signal. In this paper, two probability thresholds are selected for defining the signal peak: β= -4 and -5.


    The CCDFs of the original and crest-factor-reduced OFDM time sequences are shown in Fig. 7. Using the 10-4 probability threshold for the CFR OFDM time sequence, PAPR is 8.42 dB, which is a reduction of 1.2 dB from the 9.62 dB PAPR of the original signal. Using the 10-5 probability threshold, PAPR of the CFR and original OFDM time sequences are 8.56 dB and 10.54 dB, respectively. That is, CFR reduces PAPR by 2 dB when the 10-5 threshold is used. The crest-factor-reduced waveform meets the target PAPR of 8.5 dB for the 10-4 probability threshold, which is used more commonly in PA design than the 10-5 threshold.

 


    The BER introduced by the CFR is 0.00019 (327 bit reversals from 1730460 bits sent). The EVM, including the bit reversals, is 0.0725, which is high for 64-QAM. The limit for 3/4 rate 64-QAM is 0.0282. However, when using the easier measure that excludes the contribution from bit reversals, EVM is 0.0119. This EVM level is considered acceptable. Most of the EVM for this second measure is due to the outward expansion of the constellation, which does not increase BER at the receiver.


    This approach does not involve trying to achieve the lowest CFR. Instead, a bounded CFR is created to ease the design of the PA and digital circuitry and to generate a low BER. With this type of CFR, 90% of the CFR symbols are transmitted without modification. For such pass-through cases, only the PAPR measurement is required, and no additional IFFTs are computed.


5 Conclusion
    A CFR method that is suitable for WiMAX and other OFDM signals has been presented. Degradation associated with CFR is restricted to selected data subcarriers whose data elements are mapped onto the outer boundary of the IQ constellation. Subcarrier components correlated to the phase profiles of the primary and secondary peaks are identified for modification by outward expansions and bit reversals. The peak-to-average power for the WiMAX signal is reduced to a target level, and this allows the PA in the transmitter to be designed for high PAE. CFR is achieved with an acceptable amount of in-band BER and EVM degradation.


References
[1] IEEE 802.16-2009, IEEE Standard for Local and Metropolitan Area Networks Part 16: Air Interface for Broadband Wireless Access Systems, P802.16Rev2/D9, Jan. 2009.
[2] S. C. Cripps, RF Power Amplifiers for Wireless Communications, Norwood, MA: Artech House, 1999.
[3] R. N. Braithwaite, “Crest factor reduction system and method for OFDM transmission systems using selective sub-carrier degradation,” US patent application 20070140367, June 21, 2007.
[4] M. J. Hunton, “System and method for peak power reduction in spread spectrum communications systems,” US patent 6449362, Sept. 10, 2002.
[5] M. J. Hunton, “System and method for post filtering peak power reduction in multi-carrier communications systems,” US patent 7,095,798, Aug. 22, 2006.
[6] G. A. Awater, R. D. de Wild, A. Hendrik, “Transmission system and method employing peak cancellation to reduce the peak-to-average power ratio,” US patent 6,175,551, Jan. 16, 2001.
[7] M. J. Hunton, “OFDM communications system employing crest factor reduction with ISI control,” US patent application 20070058743, March 15, 2007.
[8] B. S. Krongold and D. L. Jones, “PAR reduction in OFDM via active constellation extension,” IEEE Trans. Broadcasting, vol. 49, no. 3, pp. 258-268, Sept. 2003.
[9] S. H. Han and J. H. Lee, “PAPR reduction of OFDM signals using a reduced complexity PTS technique,” IEEE Signal Proc. Lett., vol. 10, no. 11, pp. 887-890, Nov. 2004.
[10] L. J. Cimini, Jr. and N. R. Sollenberger, “OFDM communication system and method having a reduced peak-to-average power ratio,” US patent 6928084, Aug. 9, 2005.
[11] A. Alavi and C. Tellambura, “PAPR reduction of OFDM signals using partial transmit sequence: an optimal approach using sphere decoding,” IEEE Commun. Lett., vol. 9, no. 11, pp. 982-984, Nov. 2005.
[12] C.-L. Wang and Y. Ouyang, “Low-complexity selected mapping schemes for peak-to-average power ratio reduction in OFDM systems,” IEEE Trans. Signal Processing, vol. 53, no. 12, pp. 4652-4660, Dec. 2004.
[13] R. N. Braithwaite, “Crest factor reduction for down-link LTE by transmitting phase shifted resource blocks without side information,” European Wireless Conf., EuWIT 2009, Rome, Italy, pp. 13-16.
[14] S. Hosokawa, S. Ohno, K. D. Teo, and T. Hinamoto, “Pilot tone design for peak-to-average power ratio reduction in OFDM,” IEEE Int. Sym. Circ. Syst. (ISCAS 2005), Kobe, Japan, pp. 6014-6017.
[15] L. Guan and A. Zhu, “Gaussian pulse-based two-threshold parallel scaling tone reservation for PAPR reduction of OFDM signals,’ Int. J. Digital Multimedia Broadcasting, vol. 2011, Article ID 470310, 9 pages, 2011. doi:10.1155/2011/470310.
[16] Y. J. Kou, W.-S. Lu, and A. Antoniou, “Peak-to-average power ratio reduction algorithms for OFDM systems via constellation extension,” IEEE Int. Sym. Circ. Syst. (ISCAS 2005), Kobe, Japan, pp. 2615-2618.
[17] R. N. Braithwaite, “General principles and design overview of digital predistortion,” chapter in Digital Processing for Front End in Wireless Communication and Broadcasting, F. Luo (Ed.), Cambridge Univ. Press, 2011.

 

Biography


R. Neil Braithwaite (nbraithwaite@pwav.com) received his B.Sc. degree in electrical engineering from the University of Calgary in 1985. He received his M.Sc. and Ph.D. degrees from the University of British Columbia in 1989 and 1992. From 1992 to 1995, he conducted postdoctoral research at the University of California, Riverside. From 1985 to 1987 and 1995 to 2002, he worked for Computing Devices Company (Canada), Nortel (Canada), and Agilent Laboratories (USA). Since 2002, he has been working for Powerwave Technologies (USA). He is the author of several papers and patents, as well as a recent book chapter on digital predistortion in RF power amplifiers [17].

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